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INTEGRATED CIRCUITS
DATA SHEET
TEA1085; TEA1085A Listening-in circuit for line-powered telephone sets
Preliminary specification File under Integrated Circuits, IC03A March 1992
Philips Semiconductors
Preliminary specification
Listening-in circuit for line-powered telephone sets
FEATURES * Internal supply optimum current split-up - low constant current (adjustable) in transmission IC - nearly all line current available for listening-in adjustable supply voltage * Loudspeaker amplifier dynamic limiter providing low distortion and the highest possible output power SE or BTL drive for loudspeaker volume control by potentiometer and/or logic inputs (e.g. microcontroller drive) fixed gain of 35 dB * Larsen level limiter low sensitivity for own speech due to 3rd-order filter and attack delay adjustable voltage thresholds * Power down input * MUTE input TEA1085/TEA1085A - clickfree switching between listening-in mode and standby mode TEA1085 - toggle function - start-up in standby condition TEA1085A - logic level input ORDERING INFORMATION EXTENDED TYPE NUMBER TEA1085/TEA1085A TEA1085T/TEA1085AT Notes 1. SOT101-1; 1998 Jun 18. 2. SOT137-1; 1998 Jun 18. PACKAGE PINS 24 24 PIN POSITION DIL SO24
TEA1085; TEA1085A
GENERAL DESCRIPTION The TEA1085 and TEA1085A are bipolar ICs which have been designed for use in line-powered telephone sets and provide a listening-in facility for the received line signal via a loudspeaker. Nearly all the line current can be used for powering the loudspeaker. The circuits incorporate a supply circuit, loudspeaker amplifier dynamic limiter, MUTE circuit, power-down facility and logic inputs for gain setting. The devices also incorporate a Larsen Level Limiter to reduce howling effects. The ICs are intended for use in conjunction with a transmission circuit of the TEA1060 family.
MATERIAL plastic plastic
CODE SOT101B(1) SOT137A(2)
March 1992
2
Philips Semiconductors
Preliminary specification
Listening-in circuit for line-powered telephone sets
QUICK REFERENCE DATA SYMBOL ISUP VBB ISUP Gv PARAMETER input current range stabilized supply voltage current consumption voltage gain loudspeaker amplifier SE BTL Gv ISUP maximum gain reduction with logic inputs (3 steps) minimum input current POUT = 20 mW typ. into 50 SE POUT = 40 mW typ. into 50 BTL tad(RMS) VDTI(RMS) Gv Tamb Larsen limiter attack delay time VDTI jumps from 0 to 100 mV (RMS value) Larsen limiter threshold level Larsen limiter preamplifier gain setting range operating ambient temperature range Larsen mode PD = HIGH CONDITIONS
TEA1085; TEA1085A
MIN. 4 - - - - -
TYP. - 3.6 55 35 41 18
MAX. 120 - - - - -
UNIT mA V A dB dB dB
- - 100 - 30 -25
15 - - 7 - -
17 32 200 - 52 +75
mA mA ms mV dB C
March 1992
3
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ndbook, full pagewidth
March 1992
line
(1)
Philips Semiconductors
Listening-in circuit for line-powered telephone sets
VBB
(1)
TEA1060 (LN)
SREF SUP 4 2
SDC 3
THL1 THL2 LLC 14 13 12
DCA 16
DTI 15
QLA 11 9 LAI-
TEA1060 (MIC)
VSS 1 VBB 24 PD 19 VA 18
(1)
SUPPLY PD
LARSEN LEVEL LIMITER
PREAMPLIFIER LARSEN LEVEL LIMITER 10 LAI+
4 VBB TEA1060 (MIC) VBB 2 2 2
GSC1 8 GSC2 7
(1)
TEA1085 TEA1085A
START CIRCUIT
4
SIC 17
I-STABILIZATION LOGIC GAIN CONTROL
21 QLS1 PEAK AND CURRENT LIMITER 23 DLC RECEIVING AMPLIFIER MUTE 20 MUTE 5 LSI1 6 LSI2
MGR032
POWER AMPLIFIER
22 QLS2
TEA1085; TEA1085A
(1)
Preliminary specification
(1)
(2)
TEA1060 (VEE) TEA1060 (QR)
(1) To TEA1060 (SLPE). (2) See Fig.16.
Fig.1 Block diagram.
Philips Semiconductors
Preliminary specification
Listening-in circuit for line-powered telephone sets
PIN CONFIGURATION SYMBOL PIN VSS SUP SDC SREF LSI1 LSI2 GSC2 GSC1 LAI- LAI+ QLA LLC THL2 THL1 DTI DCA SIC VA PD MUTE QLS1 QLS2 DLC VBB 1 2 3 4 5 6 7 8 9 10 11 12 13 14 15 16 17 18 19 20 21 22 23 24 DESCRIPTION negative supply positive supply supply amplifier decoupling supply reference input loudspeaker amplifier input 1 loudspeaker amplifier input 2 logic input 2 for gain select logic input 1 for gain select Larsen limiter preamplifier inverting input Larsen limiter preamplifier non-inverting input Larsen limiter preamplifier output Larsen limiter capacitor Larsen limiter residual threshold level Larsen limiter attack delay threshold level Larsen limiter detector input Larsen limiter detector current adjustment Larsen limiter current stabilizer VBB voltage adjustment power-down input MUTE input loudspeaker amplifier output 1 loudspeaker amplifier output 2 dynamic limiter capacitor stabilized supply decoupling
GSC1 8 LAI- 9 LAI+ 10 QLA 11 LLC 12
handbook, halfpage
TEA1085; TEA1085A
VSS 1 SUP 2 SDC 3 SREF 4 LSI1 5 LSI2 6 GSC2 7
24 VBB 23 DLC 22 QLS2 21 QLS1 20 MUTE
TEA1085 19 PD TEA1085A 18 VA
17 SIC 16 DCA 15 DTI 14 THL1 13 THL2
MLA415
Fig.2 Pin configuration.
March 1992
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Philips Semiconductors
Preliminary specification
Listening-in circuit for line-powered telephone sets
FUNCTIONAL DESCRIPTION Figure 1 illustrates a block diagram of the TEA1085/TEA1085A with external components and connections to the transmission IC. The TEA1085/TEA1085A are bipolar ICs which have been designed for use in line-powered telephone sets and provide a listening-in facility for the received line signal via a loudspeaker. Nearly all the line current can be used for powering the loudspeaker. The loudspeaker amplifier consists of a preamplifier, to amplify the earpiece signal from the transmission circuit and, a double push-pull output stage to drive the loudspeaker in the BTL (bridge tied load) or SE (single ended) configuration. The gain of the preamplifier is controlled by a dynamic limiter which prevents high distortion of the loudspeaker signal. This is achieved by preventing clipping of the loudspeaker signal, with respect to the supply voltage, and at too low supply current. Two logic inputs can be used to reduce the gain in 3 steps. Because of acoustic feedback from the loudspeaker to the microphone, howling signals (Larsen effect) can occur on the telephone line and in the loudspeaker. When the Larsen signal exceeds a voltage and time duration threshold the Larsen level limiter (LLL) will reduce the
TEA1085; TEA1085A
Larsen signal to a low level within a short period of time by reducing the gain of the receiving preamplifier. This is achieved by using the microphone signal as an input signal which is processed in the LLL via a preamplifier and 3rd-order filter. The MUTE input can be used to enable or disable the loudspeaker amplifier. The MUTE function of the TEA1085 has a toggle input to permit the use of a simple push-button switch. The MUTE function of the TEA1085A has a logic input to operate with a microcontroller. By activating the power-down input the current consumption of the circuit will be reduced, this enables pulse dialling or flash (register recall). An internal start circuit ensures normal start-up of the transmission IC and start-up of the listening-in IC in the standby mode. The TEA1085/TEA1085A are intended for use in conjunction with a member of the TEA1060 family and should be connected between LINE and SLPE of the transmission IC. The transmission characteristics (impedance, gain settings, for example) are not affected. The interconnection between the two ICs is illustrated in Fig.3.
handbook, full pagewidth
VCC
LN MIC+
SREF LAI+
SUP
TEA1060
LINE VEE
TEA1085
MIC- QR SLPE LSI1 LSI2 LAI- TEA1085A
QLS
VSS
MGR033
to TEA1060 (SLPE)
Fig.3 Interconnection of the TEA1085/TEA1085A with the TEA1060.
March 1992
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Philips Semiconductors
Preliminary specification
Listening-in circuit for line-powered telephone sets
Supply; SUP, SREF, VBB, VSS and VA
TEA1085; TEA1085A
The line current is divided into ITR for the TEA1060 and ISUP for the TEA1085/TEA1085A. The supply arrangement is illustrated in Fig.4.
handbook, full pagewidth
Iline
ISUP
SUP
TR1
VBB
ICC
R1
ITR
R20 Vint TR2 IBBO VOLTAGE STABILIZER IBIAS VSS VA R38
MGR034
VCC
LN SREF C20
TEA1060
LINE VEE SLPE
TEA1085 TEA1085A
R9
ITR is constant: ITR = Vint / R20; ISUP = Iline - ICC - ITR
Fig.4 Supply arrangement.
Where: Vint is an internal temperature compensated reference voltage with a typical value of 315 mV between SUP and SREF is a resistor between SUP and SREF is the internal current consumption of the TEA106X ( 1 mA)
VA and VSS or decreased by connecting this resistor between VA and VBB. The minimum level on VBB is restricted to 3.0 V; the level of the VBB limiter is also affected (see application report for further information). The supply at VBB is decoupled by a 470 F capacitor. The DC voltage (VSUP - VSS) is determined by the transmission IC (VLN-SLPE); thus: VSUP - VSS = VLN-SLPE + Vint. The minimum DC voltage that can be applied to this input is VBB(max) + 0.4 V. Where: VBB(max) is the worst case supply voltage (this depends on the setting of R38, which is connected between VA and VSS). The internal current consumption of the TEA1085/TEA1085A (ISUP0) is typically 4.2 mA (where VSUP - VSS = 4.5 V, MUTE off). Thus the current available for powering the loudspeaker is ISUP - ISUP0. The current ISUP0 consists of a bias current of 0.4 mA for the circuitry connected to SUP and current IBB0 of 3.8 mA which is used for the circuitry connected to VBB (see Fig.4).
R20 ICC
A practical value for R20 is 150 . This value of resistance produces a value for ITR = 2 mA and ISUP = Iline - 3 mA. The TEA1085/TEA1085A stabilizes its own supply voltage at VBB. Transistor TR1 provides the supplies for the internal circuits. TR2 is used to minimize the signal distortion on the line by momentarily diverting the input current to VSS whenever the instantaneous value of the voltage VSUP drops below the supply voltage VBB. VBB is fixed to a typical value of 3.6 V but can be increased by means of an external resistor (R38) connected between
March 1992
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Philips Semiconductors
Preliminary specification
Listening-in circuit for line-powered telephone sets
TEA1085; TEA1085A
Logic gain control (GSC1 and GSC2) pins 7 and 8
ndbook, halfpage
5.5
MGR035
VBB (V)
The logic inputs GSC1 and GSC2 can be used to reduce the gain of the loudspeaker amplifier by means of the logic gain control function in 3 steps of 6 dB. Table 1 GSC2 0 Data for microcontroller drive of logic inputs GSC1 0 1 0 1 gain (dB) 35 28.7 22.2 17 gain reduction (dB) 0 6.3 12.2 18
5.1
4.7
4.3
0 1 1
VBB = 3.60 V 102 R38 (k) 103
3.9
Where: 0 = connection to VSS or left open-circuit 1 = applying a voltage VSS + 1.5 V
3.5 10
Fig.5
Stabilized supply voltage as a function of R38.
Supply amplifier stability (SDC) pin 3 To ensure stability of the TEA1085/TEA1085A, in combination with a transmission IC of the TEA1060 family, a 47 pF capacitor connected between SDC and SUP and a 150 H coil connected between SUP and the positive line terminal (Fig.16) is required. Loudspeaker amplifier (LSI1/LSI2 and QLS1/QLS2) pins 5/6, 21/22 The TEA1085/TEA1085A have symmetrical inputs at LSI1 and LSI2. The input signal is normally taken from the earpiece output of the transmission circuit via a resistive attenuator (see Fig.3). The amount of attenuation must be chosen in accordance with the receive gain of the transmission IC (which depends on the sensitivity of the earpiece transducer). The maximum input signal level is 450 mV(RMS) at Tamb = +25 C. The outputs QLS1 and QLS2 can be used for single ended drive (SE) or bridge tied load drive (BTL). The output stages have been optimized for use with a 50 loudspeaker (e.g. Philips type AD2071). The gain of the amplifier is fixed to 35 dB for the SE drive and 41 dB for the BTL drive (when the inputs for logic control are left open-circuit or are connected to VSS). The volume control can be obtained by using a potentiometer at the input and/or by the logic control function. March 1992 8
Philips Semiconductors
Preliminary specification
Listening-in circuit for line-powered telephone sets
Dynamic limiter (DLC) pin 23 To prevent distortion of the signal at the loudspeaker outputs the gain of the amplifier is reduced rapidly when: * the peaks of the signal at the loudspeaker outputs exceed an internally determined threshold (voltage limiter) * the DC current into SUP is insufficient (current limiter) * the voltage at VBB decreases below an internally determined threshold, typically 2.9 V (VBB limiter) The time in which the gain reduction is effected is the 'attack time'; this is very short in the first and third instance and relatively long in the second instance. The circuit will remain in the gain-reduced condition until the peaks of the output signal remain below the threshold level. The gain will then return to a nominal level after a time determined by the capacitor connected to DLC (release time).
TEA1085; TEA1085A
MUTE input (MUTE) pin 20; TEA1085A This MUTE is provided with a logic input to operate with a microcontroller for instance. The loudspeaker amplifier is disabled when the MUTE input is LOW (connected to VSS or open input). A HIGH level at the MUTE input enables the amplifier in the listening-in mode. MUTE input (MUTE) pin 20; TEA1085 The MUTE function is provided with a toggle input and is designed to switch between the standby condition and the listening-in condition on the rising edge of the input MUTE signal (see Fig.6). In the basic application the MUTE input must be LOW (connected to VSS). A simple push-button can be used to operate the MUTE toggle (see Fig.7). Debouncing can be realized by means of a small capacitor connected between MUTE and VSS. An internal start circuit ensures that the circuit always starts up in the standby condition.
handbook, full pagewidth LSI1
MUTE
QLS1 standby listening-in standby
MGR036
Fig.6 Mute toggle function of the TEA1085.
handbook, full pagewidth
VBB
MUTE 10 k
MUTE
MLA055
(a) Break contact.
(b) Make contact.
Fig.7 Mute switch alternatives with the TEA1085.
March 1992
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Philips Semiconductors
Preliminary specification
Listening-in circuit for line-powered telephone sets
Power down input (PD) pin 19 During pulse dialling or register recall (timed loop break) the telephone line is interrupted, thereby breaking the supply to the transmission and listening-in circuits. The capacitor connected to VBB provides the supply for the listening-in circuit during the supply breaks. By making the PD input HIGH during the loop break the requirement on the capacitor is eased and, consequently, the internal (standby) current consumption IBBO (Fig.4) at VBB is reduced from 3.8 mA to 400 A typical. So that the transmission circuit is not affected transistors TR1 and TR2 are inhibited and the bias current is reduced from 0.4 mA to 55 A with VSUP = 4.5 V in the following equation: ISUP(PD) = IBIAS(PD) = (VSUP - 2Vd) / Ra (where 4.2 V < VSUP < VBB + 3 V) 2Vd = the voltage drop across 2 internal diodes ( 1.3 V) Ra = an internal resistor of typical 60 k Larsen limiter current stabilizer (SIC) pin 17 A current reference is set by resistor R36 between SIC and VSS. The preferred value is 120 k. The internal reference current is given by the following equation:
TEA1085; TEA1085A
ISIC = 1.25 / R36; when R36 = 120 k, ISIC = 10.5 A Changing the value of R36 will affect the timing of the Larsen level limiter system. Larsen limiter preamplifier (LAI1/LAI2 and QLA) pins 9/10 and 11 This circuit amplifies the microphone signal to a level suitable for the Larsen limiter detector. The gain is set by external components (see Fig.8). Normally the gain is set to the same level as the microphone amplifier of the transmission circuit, this ensures that the output signal level at output QLA is equal to the line signal level. The gain between QLA and the microphone input is given by the following equation (the high-pass filter is not taken into account): Apre = VQLA / VM = R29 / R26; in the basic application R25 = R26 = 10 k The gain can be adjusted between 30 dB (R29 = 316 k) and 52 dB (R29 = 4 M). The impedance result of R28 and R27 in parallel must be equal to R29 (e.g. R27 = R28 = 2 x R29).
handbook, full pagewidth
VBB C25 R32
R29 C23 VM C22 R27 VBB R28 VSS R26 LAI-
R30
IDCA
R33 DCA
- +
QLA VQLA
C24 DTI
- +
LARSEN DETECTOR THL1 R35 THL2 R34
MGR037
R25
LAI+
R31
LLC
Fig.8 Larsen limiter preamplifier and voltage/current converter.
March 1992
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Philips Semiconductors
Preliminary specification
Listening-in circuit for line-powered telephone sets
Larsen limiter detector (DTI and DCA) pins 15 and 16 The QLA output signal is AC coupled to the detector input DTI. DTI is biased by potential divider R30 and R31. The voltage applied to DTI of the Larsen level limiter is converted into a current for further processing in this circuit. Current adjustment is achieved using the network connected between DCA and VBB (see Fig.8). The equation for DC current is: R30 1 I DCA = ---------------------------- x V BB x ---------------------------R30 + R31 R32 + R33 The equation for AC current is: V DTI 1 i DCA = ----------- for f > -- R33 C25 2 R33 In the basic application: R30 = 100 k, R31 = 220 k, R33 = 500 , R32 = 100 k and C25 = 330 nF This results in IDCA = 11 A and the equation: i DCA ----------- = 2 (mA/V) V DTI High-pass filter A third order high-pass filter is created between the microphone input voltage and the current flowing into DCA. The cut-off frequencies (see Fig.9) of the three sections are: 1 R30 x R31 f1 = ---------------------------- where R eq = ---------------------------2R eg C24 R30 + R31 1 f2 = -----------------------------2R33C24 1 f3 = ------------------------------ = 1/(2R25C22 ) 2R26C23 Where: R25 = R26 and C22 = C23 The filter reduces the sensitivity of the system to own speech. Normal speech is in the frequency range 300 Hz to 3400 Hz, however, the Larsen signal normally occurs at a frequency > 3 kHz. With the component values as used in the basic application (see Fig.16); f1 = 500 Hz, f2 = 1 kHz and f3 = 3 kHz
handbook, halfpage g
TEA1085; TEA1085A
20 log (dB)
go f1 0 6 dB per octave 12 dB per octave f2 f3 20 log f
18 dB per octave
speech
Larsen
MGR038
Fig.9 Third-order high-pass filter.
i DCA Where: g = ---------Vm
A pre g o = ---------R33
Larsen limiter capacitor (LLC) pin 12 A 1 F capacitor (C26) is connected externally between VSS and LLC to determine the attack and release timing of the Larsen level limiter in the listen-in and Larsen mode. The timing is also dependent on the value of the resistor connected between SIC and VSS. Larsen level limiter threshold (THL1 and THL2) pins 13 and 14 When the signal at DTI exceeds the first threshold level the capacitor connected to LLC will start to discharge. The first threshold level is determined by the value of the resistor, R35, connected to THL1 and VSS. The amount of discharge of C26 depends on how much the level of the signal at DTI exceeds the first threshold level (for normal speech the discharge is small). The Larsen effect is generally defined as a signal level of 100 mV(RMS), on line, for a period of more than 100 ms. The Larsen signal must be reduced to a low level within 200 ms. For Larsen signal levels (f > f3 in Fig.9) of 100 mV(RMS) at DTI and, with the component values of Fig.16, the system will switch from the listen-in mode to the Larsen mode in a time period of 100 ms to 200 ms; consequently, the initial Larsen effect will last only for a short period of time.
March 1992
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Philips Semiconductors
Preliminary specification
Listening-in circuit for line-powered telephone sets
This reaction time is the 'attack delay time' and ensures minimum sensitivity of the system for own speech. The first threshold level at DTI is determined by the equation: 1.25 I DCA V DTI1 = ---------- - ----------- x 2 x R33 ( if f > f3 in Fig.9 ) R25 2 Where: IDCA = the DC current into DCA With the component values given in Fig.16, IDCA = 11 A thus VDTI1 = 18.8 mV. Listen-in mode During normal speech the discharge of the capacitor connected to LLC is not sufficient to reach the threshold level whereby the system switches to the Larsen mode. This is because normal speech is not continuous, the discharge of C26 is slow (attack delay) and the charge is fast. The slope of VLLC during charge is given in the equation: V LLC 1.25 S 1i = ---------------- = ---------------------------- ( V s ) C26 x R36 With C26 = 1 F and R36 = 120 k this results in S1i = 10 V/s. Discharge of the capacitor at LLC occurs when the signal at DTI exceeds VDTI1, thus for a continuous signal at DTI the attack delay time tad (see Fig.10) is determined by the equation: C26 x R36 t ad = ------------------------------------2 x ( 3 x k - 1) Where k = t1 / T The duty cycle is determined by the time in which the first threshold level (VDTI1) is exceeded by the signal level at DTI (see Fig.11) thus for large signals; k 0.5. With the component values given in Fig.16; k 0.457 for signals 100 mV(RMS). Consequently 120 ms tad 160 ms, for VDTI 100 mV(RMS) Larsen mode
TEA1085; TEA1085A
After the 'attack delay time' the circuit switches from the listen-in mode to the Larsen mode. The gain of the loudspeaker amplifier is reduced quickly to a value (tLAa = Larsen attack time, see Fig.10) whereby the residual Larsen signal is determined by a second threshold level. This level can be set by resistor R34 connected between THL2 and VSS. The second threshold level must always be selected at a lower level than the first threshold level thus R34 > R35. The time taken to effect gain reduction is very short. In the Larsen mode the circuit acts as a dynamic limiter with peak detector and regulates the gain so that the signal level at DTI is determined by the second threshold level VDTI2. The second threshold level at DTI is determined by the equation: 1.25 I DCA V DTI2 = ---------- - ----------- x 2 x R33 ( if f > f3 in Fig.9 ) R34 2 Where: IDCA = the DC current into DCA With the component values given in Fig.16, VDTI2 = 6.9 mV. The charge current in the Larsen mode is reduced to half the charge current in the listen-in mode. The slope of VLLC during charge (see Fig.10) is given in the equation: V LLC 1.25 S la = ---------------- = -------------------------------------- ( V s ) 2 x C26 x R34 Where: C26 = 1 F and R36 = 100 k, Sla = 5 V/s When the Larsen effect stops (total open-loop gain < 1) the gain of the loudspeaker amplifier will return to its normal value in a time period known as the 'Larsen release time' (tLAr). This time period is determined by capacitor C26 connected to LLC and resistor R36 connected to SIC. Where: C26 = 1 F and R36 = 120 k, tLAr = 250 ms In practice the choice of the threshold levels (determined by R35 and R34) depends on the sensitivity of the microphone and loudspeaker, the send and receive gains, sidetone suppression and the acoustical properties which are determined by the cabinet of the telephone set.
March 1992
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Philips Semiconductors
Preliminary specification
Listening-in circuit for line-powered telephone sets
TEA1085; TEA1085A
handbook, full pagewidth
VDTI
slope Sli
slope Sla 0.63 V
VLLC
tad
tLAr tLAa
1 0.5 V 0V listen-in mode Larsen mode listen-in mode
MGR039
Where: Gv Change of receive gain = --------G vo
Nominal receive gain = 20 log Gvo = 35 dB
Fig.10 Dynamic behaviour of Larsen limiter (in open-loop condition).
handbook, full pagewidth
-VDTI
^
VDTI VDTI1
t1 T Where: t1 k = --T
MGR040
V DTI1 arc sin -------------- V DTI k = 0.5 - --------------------------------------
Fig.11 Definition of duty cycle k.
March 1992
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Philips Semiconductors
Preliminary specification
Listening-in circuit for line-powered telephone sets
LIMITING VALUES In accordance with the Absolute Maximum System (IEC 134) SYMBOL VSUP continuous during switch-on or line interruption repetitive supply voltage from 1 ms to 5 s with 12 current limiting resistor in series with supply PARAMETER positive supply voltage CONDITIONS
TEA1085; TEA1085A
MIN. - - - 12
MAX.
UNIT V V V
13.2 28
VSREF Vn ISUP
supply reference voltage voltage on all other pins supply current TEA1085/TEA1085A TEA1085T/TEA1085AT see Fig.12 see Fig.13 Tamb = 75 C; Tj = 125 C
VSS - 0.5 VSS - 0.5 - -
VSUP + 0.5 VBB + 0.5 120 120
V V mA mA
Ptot
total power dissipation TEA1085/TEA1085A TEA1085T/TEA1085AT
- - -25 -40 -
1 666 +75 +125 +125
W mW C C C
Tamb Tstg Tj
operating ambient temperature range storage temperature range junction temperature
THERMAL RESISTANCE SYMBOL Rth j-a PARAMETER from junction to ambient in free air TEA1085/TEA1085A TEA1085T/TEA1085AT Note 1. Device mounted on a glass epoxy board 40.1 x 19.1 x 1.5 mm. note 1 50 K/W 75 K/W CONDITIONS THERMAL RESISTANCE
March 1992
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Philips Semiconductors
Preliminary specification
Listening-in circuit for line-powered telephone sets
TEA1085; TEA1085A
MGR041
MGR042
handbook, halfpage
130 ISUP (mA)
handbook, halfpage
(1) (2) (3)
130 ISUP (mA)
110
110
(2) (3)
(1)
90
90
(5)
(4)
70
70
50
50
30 2 4 6 8 10 12 VSUP (V)
30 2 4 6 8 10 12 VSUP (V)
(1) Tamb = 55 C; Ptot = 1.4 W. (2) Tamb = 65 C; Ptot = 1.2 W. (3) Tamb = 75 C; Ptot = 1.0 W.
(1) Tamb = 35 C; Ptot = 1.2 W. (2) Tamb = 45 C; Ptot = 1.07 W. (3) Tamb = 55 C; Ptot = 0.93 W. (4) Tamb = 65 C; Ptot = 0.8 W. (5) Tamb = 75 C; Ptot = 0.666 W.
Fig.12 TEA1085/TEA1085A safe operating area.
Fig.13 TEA1085T/TEA1085AT safe operating area.
March 1992
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Philips Semiconductors
Preliminary specification
Listening-in circuit for line-powered telephone sets
TEA1085; TEA1085A
CHARACTERISTICS VSREF = 4.2 V; VSS = 0 V; ISUP = 15 mA; VSUP = 0 V(RMS); f = 800 Hz; Tamb = 25 C; PD = LOW; MUTE (TEA1085) = OFF (listening-in mode); MUTE (TEA1085A) = HIGH (listening-in mode); GSC1 = GSC2 = LOW; 50 loudspeaker; no R38; test circuit Fig.14; unless otherwise specified SYMBOL Supplies VSUP VBB VBB minimum DC input voltage stabilized supply voltage variation from ISUP = 15 to 120 mA R38 = 39.2 k between pins VSS and VA; VSREF = 5.2 V; ISUP = 15 mA VBB /T ISUP THD Vno(RMS) variation with temperature minimum operating current distortion of AC signal on SUP VSUP(RMS) = 1 V noise between SUP and VEE current consumption in power-down condition ISUP IBB |Zi| input impedance single ended differential Gv voltage gain with 50 load ISUP = 15 mA; Vi = 1.8 mV(RMS) single ended BTL output Gv variation with signal level ISUP = 50 mA; Vi = 1.8 mV(RMS) and 14 mV(RMS) single ended BTL output Gv variation with frequency referred to 1 kHz f = 300 Hz and 3400 Hz; Vi = 1.8 mV(RMS) single ended BTL output Gv variation with temperature referred to 25 C Tamb = -25 to +75 C single ended BTL output March 1992 16 - - 0.4 0.5 - - dB dB - - 0.1 0.1 - - dB dB - - +0.1 +0.2 0.4 0.6 dB dB 34 39.9 35 40.9 36 41.9 dB dB 7.5 15 9.5 19 11.5 23 k k PD = HIGH VSUP = 4.5 V VBB = 3.6 V - - 55 400 75 550 A A no R38; ISUP = 15 mA no R38; ISUP = 15 mA - 275 3.4 - 4.2 VBB + 0.7 315 3.6 10 4.45 - 355 3.8 - 4.7 V mV V mV V VSUP-SREF internal reference voltage PARAMETER CONDITIONS MIN. TYP. MAX. UNIT
tbf - - -
-0.2 4.2 0.3 -72
tbf 5.5 - -
V mA % dBmp
Loudspeaker amplifier inputs LSI1 and LSI2
Philips Semiconductors
Preliminary specification
Listening-in circuit for line-powered telephone sets
SYMBOL PARAMETER CONDITIONS MIN.
TEA1085; TEA1085A
TYP.
MAX.
UNIT
Loudspeaker outputs QLS1 and QLS2 Vo(p-p) output voltage (peak-to-peak value) single ended bridge tied load THD total harmonic distortion single ended bridge tied load Vo(p-p) output voltage (peak-to-peak value) single ended Dynamic limiter THD total harmonic distortion single ended bridge tied load tatt dynamic behaviour of limiter attack time; Vi jumps from 10 mV(RMS) to 65 mV(RMS) voltage limiter current limiter VBB limiter trel VBBO Vno(RMS) release time; Vi jumps from 65 mV(RMS) to 10 mV(RMS) threshold VBB limiter below which gain reduction starts noise output voltage Vi = 22 mV(RMS) +10 dB ISUP = 9 mA ISUP = 17 mA ISUP = 23.5 mA single ended load - - - 0.5 1.2 0.6 10 10 10 % % % Vi = 22 mV(RMS) ISUP = 9 mA; note 1 ISUP = 17 mA; note 2 ISUP = 23.5 mA; note 2 ISUP = 32 mA; note 3 Vi = 22 mV(RMS) ISUP = 9 mA ISUP = 17 mA ISUP = 23.5 mA Vi = 22 mV(RMS) ISUP = 17 mA; VSUP - VEE = 1 V(RMS) 1.75 2.15 - V - - - 0.4 0.7 0.4 2 2 2 % % % 1.2 2.5 2.5 3.5 1.45 2.9 2.9 4.0 - - - - V V V V
ISUP = 17 mA ISUP = 12 mA ISUP = 9 mA ISUP = 17 mA ISUP = 9 mA 1 k between inputs LSI1, LSI2; psophometrically weighted (P53 curve)
- - - tbf tbf
2 500 10 75 2.95
5 tbf - tbf tbf
ms ms ms ms V
single ended bridge tied load Logic gain control Gv reduction of voltage gain GSC2 = 0, GSC1 = 1 GSC2 = 1, GSC1 = 0 GSC2 = 1, GSC1 = 1 March 1992 17 Vi = 1.8 mV(RMS)
- -
170 350
- -
V V
5.8 11.7 17
6.3 12.2 18
6.8 12.7 19
dB dB dB
Philips Semiconductors
Preliminary specification
Listening-in circuit for line-powered telephone sets
SYMBOL PARAMETER CONDITIONS MIN.
TEA1085; TEA1085A
TYP.
MAX.
UNIT
Larsen limiter preamplifier operational amplifier Gv0 fp1 fp2 GB Gv open-loop gain 1st pole 2nd pole unity gain bandwidth voltage gain f = 3 kHz; R26 = 10 k; R29 = 4 M - - - - 51 92 120 3.3 4 52 - - - - 53 dB Hz MHz MHz dB
Gv
gain adjustment range
30
-
52
dB
Larsen limiter detector voltage to current convertor VDCA-VDTI DC offset voltage Gv VTHL1 VTHL2 voltage gain from DTI to DCA DC voltage at THL1 DC voltage at THL2 dynamic behaviour with a burst at DTI tLIr tad listen-in release time attack delay time VDTI jumps from 0 to 100 mV (RMS value) VDTI jumps from 0 to 1 V (RMS value) tLAa tLAr Larsen attack time Larsen release time VDTI jumps from 100 mV to 0 mV (RMS value) VLLC -VLLC Gv DC voltage at LLC reduction of VLLC to attack Larsen mode gain reduction VLLC = 0.7 V VDTI = 0 V see Fig.15(b); VDTI = 100 mV(RMS) see Fig.15(b) tbf 250 tbf ms VBB - VDTI = 1 V VDTI = 100 mV(RMS); f = 3 kHz R35 = 51 k R34 = 100 k f = 3 kHz; see Fig.15 see Fig.15(a) see Fig.15(b) - 100 - 160 120 20 200 - tbf ms ms ms tbf 40 tbf ms -25 tbf 1.8 1.8 1 -0.8 1.25 1.25 +25 tbf 1.33 1.33 mV dB V V
1.75 0.59 60
1.9 0.63 tbf
2.0 0.68 tbf
V V dB
March 1992
18
Philips Semiconductors
Preliminary specification
Listening-in circuit for line-powered telephone sets
SYMBOL PARAMETER CONDITIONS MIN.
TEA1085; TEA1085A
TYP.
MAX.
UNIT
MUTE input; TEA1085 (toggle function, positive edge triggered set-reset flip-flop) VIL VIH IMUTE tW PR LOW level input voltage HIGH level input voltage input current minimum input pulse width minimum pulse repetition time MUTE = LOW 0 1.5 - - - tbf MUTE = ON 60 - - -22 50 2 2 100 0.3 VBB + 0.4 -28 - - tbf - V V A s ms V dB
VBB(MUTE) supply voltage below which MUTE toggle is reset Gv reduction of gain from LSI1, LSI2 to QLS1, QLS2
MUTE input; TEA1085A VIL VIH IMUTE Gv LOW level input voltage HIGH level input voltage input current reduction of gain from LSI1, LSI2 to QLS1, QLS2 MUTE = HIGH MUTE = HIGH 0 1.5 - 60 - - 10 100 0.3 VBB + 0.4 20 - V V A dB
Power down input VIL VIH IPD VIL VIH IGSC Notes 1. Typical output power is 5 mW into 50 2. Typical output power is 20 mW into 50 3. Typical output power is 40 mW into 50 LOW level input voltage HIGH level input voltage input current PD = HIGH 0 1.5 - - - 2.3 - - 6 0.3 VBB + 0.4 2.8 V V A
Logic inputs GSC1 and GSC2 LOW level input voltage HIGH level input voltage input current GSC = HIGH 0 1.5 - 0.3 VBB + 0.4 8 V V A
March 1992
19
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IIN A ICC R1 ILN R20 C21 R35 R34 C26 R33 R29 R26 9 VBB 7 3 Iline C1 Vm R27 R25 C22 C23 ISUP 15 1 8 2 4 19 2 3
Philips Semiconductors
(1)
14
agewidth
Listening-in circuit for line-powered telephone sets
R30 VBB R32
(1) (1)
R31
(1)
C25
C24
VDTI
13
12
16
15
11
TEA1060
VLSI 6
5
TEA1085 TEA1085A
10 R28
6 C27 21 RL 50
20
(1) To TEA1060 (SLPE) The DC current is divided as follows: V SUP - SREF I SUP = I IN - -----------------------------R20 V SUP - SREF I LN = -----------------------------R20
5 10 9 16 18 1 24 18 20 8 7 23 17
22
R5
C3
R9
C20 C31
(1) (1)
C28
R36
MGR043
(1) (1)
(1)
VBB
VBB
TEA1085; TEA1085A
for for TEA1085 TEA1085A
Preliminary specification
The pins not shown in the TEA1060 are left open. An impedance in series with pin SUP (e.g. an ammeter) should be avoided as it interferes with the value of ILN.
Fig.14 Test circuit.
Philips Semiconductors
Preliminary specification
Listening-in circuit for line-powered telephone sets
Table 2 Component values in test circuit Fig.14 CONDITION VALUE UNIT k k k M M M k k k k k k F F F pF F F nF nF F F nF nF
TEA1085; TEA1085A
COMPONENT Resistor R1 R5 R9 R20 R25 R26 R27 R28 R29 R30 R31 R32 R33 R34 R35 R36 Capacitor C1 C3 C20 C21 C22 C23 C24 C25 C26 C27 C28 C31
620 3.6 20 150 10 10 8 8 4 100 220 100 500 100 51 120
100 4.7 470 68 2.2 2.2 100 330 1 220 330 TEA1085 only 10
March 1992
21
Philips Semiconductors
Preliminary specification
Listening-in circuit for line-powered telephone sets
TEA1085; TEA1085A
handbook, full pagewidth
VDTI
VDTI
200 ms VLLCO 0.63 V VLLC VLLC
100 ms
tLIr tad tLAa tLAr
MGR044
(b) Attack delay (tad), Larsen attack time (tLAa), Larsen release time (tLAr); VDTI = 100 mV(RMS) and 1 V(RMS); f = 3 kHz.
(a) Listen-in release time (tLIr); VDTI = 100 mV(RMS); f = 3 kHz.
Fig.15 Test signals for Larsen level limiter.
March 1992
22
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L1 R1 R20 15 C1 1 12 8 DP 7 TONE LINE DIALLER DP DP 13
APPLICATION INFORMATION
Philips Semiconductors
4 19
handbook, full pagewidth
Listening-in circuit for line-powered telephone sets
R30 VBB R32
(1) (1) (1)
R31
(1)
C25
C21
R35
R34
C26
R33
C24
2
3
14
13
12
16
15
11 9
R29 R26 VBB C23
to TEA1060 pins 7 and 8
TEA1060
C2 5 R24 C29 RV20 C30 6 5
TEA1085 TEA1085A
R27 R25 C22 10 R28
23
C27 21 22 1 24 18 20 8 7 23 17
(1)
10
16
18
DP
C3
R9
C11
C32
C20
R38 C31
C28
R36
MLA039
TEA1085; TEA1085A
(1)
(1)
(1) (1)
(1)
(1)
interrupt
VBB
VBB
Preliminary specification
for for TEA1085 TEA1085A
(1) To TEA1060 (SLPE).
Fig.16 Basic application of TEA1085/TEA1085A and TEA1060.
Philips Semiconductors
Preliminary specification
Listening-in circuit for line-powered telephone sets
TEA1085; TEA1085A
The basic application circuit of the TEA1085/TEA1085A is illustrated in Fig.16. Only the most important components of the TEA1060 part are shown, other components and their values are given in the TEA1060 Data sheet. The supply pin (VBB) of the TEA1085/TEA1085A can also be used to supply peripheral circuits (e.g. microcontrollers, diallers etc.). Further information will be published in the TEA1085 application report. Table 3 Component values in application circuit Fig.16 CONDITION VALUE UNIT k k k M M M k k k k k k k
COMPONENT Resistor R20 R24 R25 R26 R27 R28 R29 R30 R31 R32 R33 R34 R35 R36 RV20 Capacitor C11 C20 C21 C22 C23 C24 C25 C26 C27 C28 C29 C30 C31 Coil L1 Note
150 note 1 1 10 10 note 1 note 1 note 1 3.3 3.3 1.65 100 220 100 500 100 51 120 note 1 1
4.7 470 47 4.7 4.7 4.7 330 1 47 330 220 220 TEA1085 only 10
nF F pF nF nF nF nF F F nF nF nF nF H
150
1. Value depends on the gain setting of the transmission circuit.
March 1992
24
Philips Semiconductors
Preliminary specification
Listening-in circuit for line-powered telephone sets
PACKAGE OUTLINES DIP24: plastic dual in-line package; 24 leads (600 mil)
TEA1085; TEA1085A
SOT101-1
seating plane
D
ME
A2
A
L
A1 c Z e b1 b 24 13 MH wM (e 1)
pin 1 index E
1
12
0
5 scale
10 mm
DIMENSIONS (inch dimensions are derived from the original mm dimensions) UNIT mm inches A max. 5.1 0.20 A1 min. 0.51 0.020 A2 max. 4.0 0.16 b 1.7 1.3 0.066 0.051 b1 0.53 0.38 0.021 0.015 c 0.32 0.23 0.013 0.009 D (1) 32.0 31.4 1.26 1.24 E (1) 14.1 13.7 0.56 0.54 e 2.54 0.10 e1 15.24 0.60 L 3.9 3.4 0.15 0.13 ME 15.80 15.24 0.62 0.60 MH 17.15 15.90 0.68 0.63 w 0.25 0.01 Z (1) max. 2.2 0.087
Note 1. Plastic or metal protrusions of 0.25 mm maximum per side are not included. OUTLINE VERSION SOT101-1 REFERENCES IEC 051G02 JEDEC MO-015AD EIAJ EUROPEAN PROJECTION
ISSUE DATE 92-11-17 95-01-23
March 1992
25
Philips Semiconductors
Preliminary specification
Listening-in circuit for line-powered telephone sets
TEA1085; TEA1085A
SO24: plastic small outline package; 24 leads; body width 7.5 mm
SOT137-1
D
E
A X
c y HE vMA
Z 24 13
Q A2 A1 pin 1 index Lp L 1 e bp 12 wM detail X (A 3) A
0
5 scale
10 mm
DIMENSIONS (inch dimensions are derived from the original mm dimensions) UNIT mm inches Note 1. Plastic or metal protrusions of 0.15 mm maximum per side are not included. OUTLINE VERSION SOT137-1 REFERENCES IEC 075E05 JEDEC MS-013AD EIAJ EUROPEAN PROJECTION A max. 2.65 0.10 A1 0.30 0.10 A2 2.45 2.25 A3 0.25 0.01 bp 0.49 0.36 c 0.32 0.23 D (1) 15.6 15.2 0.61 0.60 E (1) 7.6 7.4 0.30 0.29 e 1.27 0.050 HE 10.65 10.00 L 1.4 Lp 1.1 0.4 Q 1.1 1.0 0.043 0.039 v 0.25 0.01 w 0.25 0.01 y 0.1 0.004 Z
(1)
0.9 0.4 0.035 0.016
0.012 0.096 0.004 0.089
0.019 0.013 0.014 0.009
0.419 0.043 0.055 0.394 0.016
8o 0o
ISSUE DATE 95-01-24 97-05-22
March 1992
26
Philips Semiconductors
Preliminary specification
Listening-in circuit for line-powered telephone sets
SOLDERING Introduction There is no soldering method that is ideal for all IC packages. Wave soldering is often preferred when through-hole and surface mounted components are mixed on one printed-circuit board. However, wave soldering is not always suitable for surface mounted ICs, or for printed-circuits with high population densities. In these situations reflow soldering is often used. This text gives a very brief insight to a complex technology. A more in-depth account of soldering ICs can be found in our "Data Handbook IC26; Integrated Circuit Packages" (order code 9398 652 90011). DIP SOLDERING BY DIPPING OR BY WAVE The maximum permissible temperature of the solder is 260 C; solder at this temperature must not be in contact with the joint for more than 5 seconds. The total contact time of successive solder waves must not exceed 5 seconds. The device may be mounted up to the seating plane, but the temperature of the plastic body must not exceed the specified maximum storage temperature (Tstg max). If the printed-circuit board has been pre-heated, forced cooling may be necessary immediately after soldering to keep the temperature within the permissible limit. REPAIRING SOLDERED JOINTS Apply a low voltage soldering iron (less than 24 V) to the lead(s) of the package, below the seating plane or not more than 2 mm above it. If the temperature of the soldering iron bit is less than 300 C it may remain in contact for up to 10 seconds. If the bit temperature is between 300 and 400 C, contact may be up to 5 seconds. SO REFLOW SOLDERING Reflow soldering techniques are suitable for all SO packages. Reflow soldering requires solder paste (a suspension of fine solder particles, flux and binding agent) to be applied to the printed-circuit board by screen printing, stencilling or pressure-syringe dispensing before package placement.
TEA1085; TEA1085A
Several techniques exist for reflowing; for example, thermal conduction by heated belt. Dwell times vary between 50 and 300 seconds depending on heating method. Typical reflow temperatures range from 215 to 250 C. Preheating is necessary to dry the paste and evaporate the binding agent. Preheating duration: 45 minutes at 45 C. WAVE SOLDERING Wave soldering techniques can be used for all SO packages if the following conditions are observed: * A double-wave (a turbulent wave with high upward pressure followed by a smooth laminar wave) soldering technique should be used. * The longitudinal axis of the package footprint must be parallel to the solder flow. * The package footprint must incorporate solder thieves at the downstream end. During placement and before soldering, the package must be fixed with a droplet of adhesive. The adhesive can be applied by screen printing, pin transfer or syringe dispensing. The package can be soldered after the adhesive is cured. Maximum permissible solder temperature is 260 C, and maximum duration of package immersion in solder is 10 seconds, if cooled to less than 150 C within 6 seconds. Typical dwell time is 4 seconds at 250 C. A mildly-activated flux will eliminate the need for removal of corrosive residues in most applications. REPAIRING SOLDERED JOINTS Fix the component by first soldering two diagonallyopposite end leads. Use only a low voltage soldering iron (less than 24 V) applied to the flat part of the lead. Contact time must be limited to 10 seconds at up to 300 C. When using a dedicated tool, all other leads can be soldered in one operation within 2 to 5 seconds between 270 and 320 C.
March 1992
27
Philips Semiconductors
Preliminary specification
Listening-in circuit for line-powered telephone sets
DEFINITIONS Data sheet status Objective specification Preliminary specification Product specification Limiting values
TEA1085; TEA1085A
This data sheet contains target or goal specifications for product development. This data sheet contains preliminary data; supplementary data may be published later. This data sheet contains final product specifications.
Limiting values given are in accordance with the Absolute Maximum Rating System (IEC 134). Stress above one or more of the limiting values may cause permanent damage to the device. These are stress ratings only and operation of the device at these or at any other conditions above those given in the Characteristics sections of the specification is not implied. Exposure to limiting values for extended periods may affect device reliability. Application information Where application information is given, it is advisory and does not form part of the specification. LIFE SUPPORT APPLICATIONS These products are not designed for use in life support appliances, devices, or systems where malfunction of these products can reasonably be expected to result in personal injury. Philips customers using or selling these products for use in such applications do so at their own risk and agree to fully indemnify Philips for any damages resulting from such improper use or sale.
March 1992
28
Philips Semiconductors
Preliminary specification
Listening-in circuit for line-powered telephone sets
NOTES
TEA1085; TEA1085A
March 1992
29
Philips Semiconductors
Preliminary specification
Listening-in circuit for line-powered telephone sets
NOTES
TEA1085; TEA1085A
March 1992
30
Philips Semiconductors
Preliminary specification
Listening-in circuit for line-powered telephone sets
NOTES
TEA1085; TEA1085A
March 1992
31
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For all other countries apply to: Philips Semiconductors, International Marketing & Sales Communications, Building BE-p, P.O. Box 218, 5600 MD EINDHOVEN, The Netherlands, Fax. +31 40 27 24825 (c) Philips Electronics N.V. 1998
SCA60
All rights are reserved. Reproduction in whole or in part is prohibited without the prior written consent of the copyright owner. The information presented in this document does not form part of any quotation or contract, is believed to be accurate and reliable and may be changed without notice. No liability will be accepted by the publisher for any consequence of its use. Publication thereof does not convey nor imply any license under patent- or other industrial or intellectual property rights.
Printed in The Netherlands
415102/00/02/pp32
Date of release: March 1992
Document order number:
9397 750 nnnnn

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